Circuits, devices and methods related to half-bridge combiners

ABSTRACT

A half-bride combiner can be implemented as a coupling circuit having a common node and configured to couple the common node to one of first and second groups of filters through a first path and to couple the common node to the other group through a second path. The coupling circuit can be further configured such that the impedance provided by each filter of the one of the first and second groups for a signal in each band of the other group results in the signal being sufficiently excluded from the first path.

CROSS-REFERENCE TO RELATED APPLICATION(S)

This application claims priority to U.S. Provisional Application Nos.63/005,424 filed Apr. 5, 2020, entitled ARCHITECTURES HAVING BRIDGECOMBINERS AND MULTIPLEXERS, 63/005,425 filed Apr. 5, 2020, entitledBRIDGE COMBINERS, PHASE SHIFTERS AND/OR RESONATORS FOR WIRELESSAPPLICATIONS, 63/005,426 filed Apr. 5, 2020, entitled SWITCHING CIRCUITSFOR BRIDGE COMBINERS, 63/005,427 filed Apr. 5, 2020, entitled CIRCUITS,DEVICES AND METHODS RELATED TO HALF-BRIDGE COMBINERS, and 63/005,421filed Apr. 5, 2020, entitled BRIDGE COMBINERS AND FILTERS FORRADIO-FREQUENCY APPLICATIONS, the disclosure of each of which is herebyexpressly incorporated by reference herein in its entirety.

BACKGROUND Field

The present disclosure relates to bridge combiners and related circuitsfor radio-frequency (RF) applications.

Description of the Related Art

In radio-frequency (RF) applications, a signal having a plurality offrequency components can be routed from a common path to separate paths.In reverse, a plurality of signals can be routed from respective pathsto a common path. Either or both of such functionalities allow, forexample, carrier aggregation of a plurality of RF signals.

SUMMARY

In accordance with some implementations, the present disclosure relatesto a radio-frequency architecture that includes a first group ofplurality of filters each configured to support a band such that a firstfrequency range covers the respective plurality of bands, and a secondgroup of one or more filters each configured to support a band such thata second frequency range covers the respective one or more bands. Eachfilter of one of the first and second groups is configured to provide animpedance at or near a short circuit impedance for a signal in each bandof the other group, and each filter of the other group is configured toprovide an approximately open circuit impedance for a signal in eachband of the one of the first and second groups. The radio-frequencyarchitecture further includes a coupling circuit having a common nodeand configured to couple the common node to one of the first and secondgroups through a first path and to couple the common node to the othergroup through a second path. The coupling circuit is further configuredsuch that the impedance provided by each filter of the one of the firstand second groups for the signal in each band of the other group resultsin the signal being sufficiently excluded from the first path.

In some embodiments, the coupling circuit can be further configured suchthat the approximately open circuit impedance provided by each filter ofthe other group for the signal in each band of the one of the first andsecond groups results in the signal being substantially excluded fromthe second path.

In some embodiments, the first group can be the one of the first andsecond groups and be configured to support a frequency range that islower than a frequency range supported by the second group. In someembodiments, the coupling circuit can include an LC circuit that couplesthe common node to ground, with the LC circuit including an inductance Land a capacitance C in series such that the inductance L is between thecommon node and a first node and the capacitance C is between the firstnode and the ground, with the first node being coupled to the firstgroup through the first path. The coupling circuit can be configuredsuch that the common node is coupled to the second group through thesecond path.

In some embodiments, the second group can be the one of the first andsecond groups and be configured to support a frequency range that ishigher than a frequency range supported by the first group. In someembodiments, the coupling circuit can include an LC circuit that couplesthe common node to ground, with the LC circuit including a capacitance Cand an inductance L in series such that the capacitance C is between thecommon node and a second node and the inductance L is between the secondnode and the ground, with the second node being coupled to the secondgroup through the second path. The coupling circuit can be configuredsuch that the common node is coupled to the first group through thefirst path.

In some implementations, the present disclosure relates to a packagedmodule that includes a packaging substrate configured to receive aplurality of components, and a radio-frequency circuit implemented onthe packaging substrate. The radio-frequency circuit includes a firstgroup of plurality of filters each configured to support a band suchthat a first frequency range covers the respective plurality of bands,and a second group of one or more filters each configured to support aband such that a second frequency range covers the respective one ormore bands. Each filter of one of the first and second groups isconfigured to provide an impedance at or near a short circuit impedancefor a signal in each band of the other group, and each filter of theother group is configured to provide an approximately open circuitimpedance for a signal in each band of the one of the first and secondgroups. The radio-frequency circuit further includes a coupling circuithaving a common node and configured to couple the common node to the oneof the first and second groups through a first path and to couple thecommon node to the other group through a second path. The couplingcircuit is further configured such that the impedance provided by eachfilter of the one of the first and second groups for the signal in eachband of the other group results in the signal being sufficientlyexcluded from the first path.

In some teachings, the present disclosure relates to a wireless devicethat includes one or more antennas, and a front-end module incommunication with the one or more antennas. The front-end moduleincludes a radio-frequency circuit having a first group of plurality offilters each configured to support a band such that a first frequencyrange covers the respective plurality of bands, and a second group ofone or more filters each configured to support a band such that a secondfrequency range covers the respective one or more bands. Each filter ofone of the first and second groups is configured to provide an impedanceat or near a short circuit impedance for a signal in each band of theother group, and each filter of the other group is configured to providean approximately open circuit impedance for a signal in each band of theone of the first and second groups. The radio-frequency circuit furtherincludes a coupling circuit having a common node and configured tocouple the common node to the one of the first and second groups througha first path and to couple the common node to the other group through asecond path. The coupling circuit is further configured such that theimpedance provided by each filter of the one of the first and secondgroups for the signal in each band of the other group results in thesignal being sufficiently excluded from the first path. The wirelessdevice further includes a receiver configured to process one or moresignals associated with the first and second group.

For purposes of summarizing the disclosure, certain aspects, advantagesand novel features of the inventions have been described herein. It isto be understood that not necessarily all such advantages may beachieved in accordance with any particular embodiment of the invention.Thus, the invention may be embodied or carried out in a manner thatachieves or optimizes one advantage or group of advantages as taughtherein without necessarily achieving other advantages as may be taughtor suggested herein.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 depicts an architecture that can be implemented utilizing acoupling circuit having one or more features as described herein.

FIG. 2 shows a normalized Smith chart that provides a visualrepresentation of an impedance.

FIGS. 3A and 3B depict the example impedances of FIG. 1 on thenormalized Smith chart of FIG. 2.

FIG. 4 shows an architecture that can be implemented similar to theexample of FIG. 1, where a first group of filters includes three filtersfor supporting three bands, and a second group of filters includes twofilters for supporting two bands.

FIG. 5 shows an architecture where a first group of filters includes twofilters for supporting two bands, and a second group of filters includesone filter for supporting one band.

FIG. 6 shows that in some embodiments, a filter in a first group offilter(s) and a filter in a second group of filter(s) can be configuredsuch that first and second impedances provided for first and secondpaths of a coupling circuit have complex parts that are conjugates, orapproximately conjugates, of each other.

FIG. 7 shows an architecture that can be implemented similar to theexamples of FIGS. 4 and 5, and with one or more phase shifters.

FIG. 8 shows an architecture that utilizes a plurality of couplingcircuits with a plurality of groups of filters, where at least one groupincludes a plurality of filters for supporting different bands.

FIG. 9 shows an example of an architecture where a common signal node ofa coupling circuit is coupled to an antenna, and first and second pathsfrom the coupling circuit are coupled to one or more multiplexers.

FIG. 10 shows another example of an architecture where a common signalnode of a coupling circuit is coupled to an antenna, and first andsecond paths from the coupling circuit are coupled to one or moremultiplexers.

FIG. 11 shows yet another example of an architecture where a commonsignal node of a coupling circuit is coupled to an antenna, and firstand second paths from the coupling circuit are coupled to one or moremultiplexers.

FIG. 12 shows an architecture that can be a more specific example of thearchitecture of FIG. 9.

FIG. 13 shows an architecture that can be another more specific exampleof the architecture of FIG. 9.

FIG. 14 shows an architecture that can be a more specific example of thearchitecture of FIG. 10.

FIG. 15 shows an architecture that can be another more specific exampleof the architecture of FIG. 10.

FIG. 16 shows that in some embodiments, an architecture having one ormore features as described herein can include a coupling circuit thatincludes two LC circuits that couple an input node to ground.

FIG. 17A shows that in some embodiments, an architecture having one ormore features as described herein can include a coupling circuit havinga resonator.

FIG. 17B shows that in some embodiments, the resonator of the couplingcircuit of FIG. 17A can include an acoustic resonator.

FIGS. 18A and 18B show that in some embodiments, an architecture havingone or more features as described herein can include a coupling circuithaving a half bridge configuration.

FIG. 19A shows an example architecture that includes the half-bridgecoupling circuit of FIG. 18A.

FIG. 19B shows an example architecture that includes the half-bridgecoupling circuit of FIG. 18B.

FIG. 20 shows an architecture that is a more specific example of thearchitecture of FIG. 4, utilizing the coupling circuit of FIG. 16.

FIG. 21 shows scans of impedances for the example architecture of FIG.20.

FIG. 22 shows an example of how phase shifting functionality can beutilized in an architecture that includes a coupling circuit asdescribed herein.

FIG. 23 shows another example of how phase shifting functionality can beutilized in an architecture that includes a coupling circuit asdescribed herein.

FIG. 24 shows an architecture that can be a more specific example of thearchitecture of FIG. 8, where a plurality of coupling circuits can beutilized.

FIG. 25 show an architecture that can be a more specific example of thearchitectures of FIGS. 9 and 12.

FIG. 26 show an architecture that can be a more specific example of thearchitectures of FIGS. 9 and 13.

FIG. 27 shows an architecture having switching functionalities describedherein in reference to FIGS. 11, 13 and 14.

FIG. 28 shows an example architecture that includes switchingfunctionalities to allow a plurality of coupling circuits to share acommon antenna, and also to share a common group of filters.

FIG. 29 shows an architecture that can be a more specific example of thearchitecture of FIG. 19A.

FIG. 30 shows an example architecture that utilizes a number of featuresdescribed herein.

FIG. 31 shows that in some embodiments, a radio-frequency (RF) modulecan include one or more features as described herein.

FIG. 32 depicts an example wireless device having one or moreadvantageous features described herein.

DETAILED DESCRIPTION OF SOME EMBODIMENTS

The headings provided herein, if any, are for convenience only and donot necessarily affect the scope or meaning of the claimed invention.

Among others, PCT Publication No. WO2016/033427 (InternationalApplication No. PCT/US2015/047378 titled DOMINO CIRCUIT AND RELATEDARCHITECTURES AND METHODS FOR CARRIER AGGREGATION) discloses circuits,architectures and methods related to coupling circuits that can beutilized for carrier aggregation operations. For the purpose ofdescription, such a coupling circuit can also be referred to as a bridgecircuit, a Domino circuit, or a Domino bridge circuit.

FIG. 1 depicts an architecture 700 that can be implemented utilizing acoupling circuit 100 having one or more features as described herein. Insome embodiments, such a coupling circuit can include one or more of theexamples disclosed in the above-mentioned PCT Publication No.WO2016/033427.

In the example architecture 700 of FIG. 1, the coupling circuit 100 isshown to couple a common signal node 102 to a first signal processingcomponent 701 (Band A component such as Band A filter) and a secondsignal processing component 702 (Band B component such as Band Bfilter). Configured in the foregoing manner, impedance Zin1 presented tothe coupling circuit 100 can be equal to (or approximately equal to) aload impedance (e.g., 50 Ohm) of the Band A filter for a Band A signal,and be equal to (or approximately equal to) zero for a Band B signal.Similarly, impedance Zin2 presented to the coupling circuit 100 can beequal to (or approximately equal to) a load impedance (e.g., 50 Ohm) ofthe Band B filter for the Band B signal, and be equal to (orapproximately equal to) zero for the Band A signal.

As disclosed in PCT Publication No. WO2016/033427, the coupling circuit100 can be configured to couple the foregoing first and second signalpaths associated with the Band A and Band B filters, such that theapproximately zero impedance presented by the first signal path (withBand A filter) to the signal in the second frequency band (Band Bsignal) results in the signal in the second frequency band (Band Bsignal) being substantially excluded from the first signal path, andsuch that the approximately zero impedance presented by the secondsignal path (with Band B filter) to the signal in the first frequencyband (Band A signal) results in the signal in the first frequency band(Band A signal) being substantially excluded from the second signalpath.

In the example of FIG. 1, as well as some of the other examplesdescribed herein, impedances presented by respective filters aredepicted in the context of a flow of signal(s) from a common signal node(102 in FIG. 1) to either or both of first and second signal pathsassociated with first (Band A) and second (Band B) filters. However, andas disclosed in PCT Publication No. WO2016/033427, it will be understoodthat one or more features of the present disclosure can also beimplemented in a configuration where a flow of signal(s) is in reverserelative to the foregoing configuration.

FIG. 2 shows a normalized Smith chart 710 that provides a visualrepresentation of an impedance Z=R+jX, where R is resistance and X isreactance. It is noted that for a pure capacitance, reactance X is equalto X_(C)=−1/ωC where ω=2πf, and for a pure inductance, reactance X isequal to X_(L)=ωL. Thus for a pure resistance, Z=R; for a purecapacitance, Z=jX_(C)=−j/ωC, and for a pure inductance, Z=jX_(L)=jωL. Itis also noted that an impedance in the region above the horizontal lineof the Smith chart 710 has a positive imaginary value and represents aninductive impedance, and an impedance in the region below the horizontalline of the Smith chart 710 has a negative imaginary value andrepresents a capacitive impedance.

Referring to FIG. 2, the foregoing horizontal line segment is shown tobisect the outermost circle, with the left end of the horizontal linesegment representing a short circuit (Z=0) state, and the right end ofthe horizontal line segment representing an open circuit (Z=∞) state.The mid-point of the horizontal line segment (and thus the center of theoutermost circle) represents a matched impedance state. Such a matchedimpedance state has a value of Z=1 in the normalized representation. Inan un-normalized representation, such a matched impedance state can havea value of, for example, Z=50 ohms.

In the normalized Smith chart of FIG. 2, solid-line circles areconstant-resistance circles 712 at example normalized values. Forexample, the outermost circle referenced above has a constant-resistancevalue of 0, and the successively smaller circles haveconstant-resistance values of 0.2, 0.5, 1, 2, 3, 4, 5 and 10. All ofsuch constant-resistance circles share their right-most points at theright end of the above-referenced horizontal line segment (open circuitstate).

In the normalized Smith chart 710 of FIG. 2, dash-line arcs areconstant-reactance arcs 714 at example normalized values. For example,the above-referenced horizontal line segment (an arc of aninfinite-radius circle) has a constant-reactance value of 0, and thesuccessively smaller-radius-circle arcs have constant-reactance valuesof 0.2, 0.5, 1, 2, 3, 4, 5 and 10. Such constant-reactance arcs can beprovided above and below the horizontal line segment. For the arcs abovethe horizontal line segment, the arcs share their lower-most points atthe right end of the horizontal line segment (open circuit state). Forthe arcs below the horizontal line segment, the arcs share theirupper-most points at the right end of the horizontal line segment (opencircuit state).

FIGS. 3A and 3B depict the example impedances Zin1 and Zin2 of FIG. 1,respectively, on the normalized Smith chart of FIG. 2. Moreparticularly, FIG. 3A shows Zn1 having an impedance region at or aboutthe matched impedance state (Z=1+i0) that includes impedance valuesassociated with a frequency range of the first frequency band (Band A),and an impedance region at or about the short circuit state (Z=0+i0)that includes impedance values associated with a frequency range of thesecond frequency band (Band B). Similarly, FIG. 3B shows Zn2 having animpedance region at or about the matched impedance state (Z=1+i0) thatincludes impedance values associated with the frequency range of thesecond frequency band (Band B), and an impedance region at or about theshort circuit state (Z=0+i0) that includes impedance values associatedwith the frequency range of the first frequency band (Band A).

Referring to the example of FIGS. 1 and 3, it is noted that theimpedance states for Zin1 and Zin2 of FIGS. 3A and 3B can be consideredto be ideal impedance states. However, in some embodiments, the Band Afilter of the example of FIG. 1 can be a part of a group having aplurality of filters for supporting a plurality of respective bands,with the filters of the group being connectable to the first of twopaths (e.g., the upper path associated with Zin1) associated with thecoupling circuit 100. Similarly, the Band B filter of the example ofFIG. 1 can be a part of a group having a plurality of filters forsupporting a plurality of respective bands, with the filters of thegroup being connectable to the second of two paths (e.g., the lower pathassociated with Zin2) associated with the coupling circuit 100.

For example, FIG. 4 shows an architecture 720 that can be implementedsimilar to the example of FIG. 1, but where a first group of filters 721includes three filters for supporting three bands (Band 1A, Band 1B,Band 1C), and a second group of filters 722 includes two filters forsupporting two bands (Band 2A, Band 2B). In such an architecture, acoupling circuit 100 is shown to couple a common signal node 102 to thefirst group of filters 721 and the second group of filters 722.Configured in the foregoing manner, impedance values for Zin1 arepresented to the coupling circuit 100 for a signal in the bandcorresponding to a selected one of the filters of the first group offilters 721 and for a signal in the band corresponding to a selected oneof the filters of the second group of filters 722. Similarly, impedancevalues for Zin2 are presented to the coupling circuit 100 for a signalin the band corresponding to the selected one of the filters of thesecond group of filters 722 and for a signal in the band correspondingto the selected one of the filters of the first group of filters 721.

In the example of FIG. 4, the first group of filters 721 is described ashaving three filters, and the second group of filters 722 is describedas having two filters. It will be understood that each of the first andsecond groups of filters can also be implemented with different numbersof filters.

In the example of FIG. 4, each of the first and second groups of filters721, 722 is described as having a plurality of filters. It will beunderstood that in some embodiments, one group can include a pluralityof filters, and the other group can include a single filter.

For example, FIG. 5 shows an architecture 720 where a first group offilters 721 includes two filters for supporting two bands (Band 1A, Band1B), and a second group of filters 722 includes one filter forsupporting one band (Band 2). In such an architecture, a couplingcircuit 100 is shown to couple a common signal node 102 to the firstgroup of filters 721 and the single filter of the second group 722.Configured in the foregoing manner, impedance values for Zin1 arepresented to the coupling circuit 100 for a signal in the bandcorresponding to a selected one of the filters of the first group offilters 721 and for a signal in the band corresponding to the singlefilter of the second group 722. Similarly, impedance values for Zin2 arepresented to the coupling circuit 100 for a signal in the bandcorresponding to the single filter of the second group 722 and for asignal in the band corresponding to the selected one of the filters ofthe first group of filters 721.

In the examples of FIGS. 4 and 5, a selected filter in the first group721 and a selected filter in the second group 722 can be configured soas to provide ideal impedance states, similar to the example of FIGS. 1and 3. However, with such a configuration where two selected filters areoptimized, performance can suffer significantly when using other(non-selected) filter(s) of the first and second groups 721, 722.

It is noted that in many applications, and especially when a group offilters involve a wide frequency range, it is impossible or difficult toachieve ideal impedance states (ideal matched impedance state and/orideal short circuit state) for all of the filters in the group. However,in some embodiments, even if impedances Zin1 and Zin2 are not in idealimpedance states, desired or acceptable performance can be achieved ifreal parts of the complex impedances Zin1 and Zin2 are sufficientlyclose to the respective real parts of the ideal impedance states andimaginary parts of the complex impedances Zin1 and Zin2 are configuredappropriately as described herein.

In some embodiments, each filter in a first group of filter(s) and asecond group of filter(s) can be configured such that first and secondimpedances provided for first and second paths of a coupling circuithave complex parts that are conjugates, or approximately conjugates, ofeach other. More particularly, the first impedance provided for thefirst path of the coupling circuit can be expressed as Z₁=R₁+jX, and thesecond impedance provided for the second path of the coupling circuitcan be expressed as Z₂=R₂−jX, where −jX is a conjugate of +jX of Z₁.

FIG. 6 shows the foregoing complex portion-conjugated impedances interms of the first and second impedances Zin1 and Zin2 corresponding tothe example architecture 720 of FIG. 4. In the example of FIG. 4, thethree filters (Band 1A, Band 1B, Band 1C) of the first group 721 canhave frequency bands F1A<F1B<F1C, respectively, and the two filters(Band 2A, Band 2B) of the second group 722 can have frequency bandsF2A<F2B, respectively, such that F1A<F1B<F1C<F2A<F2B.

With the foregoing configurations of the filters of the first and secondgroups 721, 722, FIG. 6 depicts Smith charts for the impedances Zin1 andZin1 of FIG. 4.

Referring to FIG. 6, impedances Zin1 for signals in the three bands(Band 1A, Band 1B, Band 1C) of the first group 721 are shown to be inregions at or close to the matched impedance value (e.g., Z=1 innormalized Smith chart), and impedances Zin1 for signals in the twobands (Band 2A, Band 2B) of the second group 722 are shown to be inregions at or close to the short circuit value (e.g., Z=0 in normalizedSmith chart). Similarly, impedances Zin2 for signals in the two bands(Band 2A, Band 2B) of the second group 722 are shown to be in regions ator close to the matched impedance value, and impedances Zin2 for signalsin the three bands (Band 1A, Band 1B, Band 1C) of the first group 721are shown to be in regions at or close to the short circuit value.

In the example of FIG. 6, each filter is shown to provide Zin1 and Zin2values having respective ones of real parts associated with matchedimpedance state (Z≈1) and short circuit state (Z≈0), and complex partsthat are conjugates of each other. More particularly, for Band 1A,Zin1=R₁+jX₁ (with R₁≈1 and X₁≠0), and Zin2=R′₁−jX₁ (with R′₁≈0 andX₁≠0), with +jX₁ and −jX₁ of Zin1 and Zin2 being conjugates of eachother, as depicted by arrow 724 a. For Band 1B, Zin1=R₂+jX₂ (with R₂≈1and X₂≈0), and Zin2=R′₂−jX₂ (with R′₂≈0 and X₂≈0), with +jX₂ and −jX₂ ofZin1 and Zin2 being conjugates of each other, as depicted by arrow 724b. For Band 1C, Zin1=R₃−jX₃ (with R₃≈1 and X₃≠0), and Zin2=R′₃+jX₃ (withR′₃≈0 and X₃≠0), with −jX₃ and +jX₃ of Zin1 and Zin2 being conjugates ofeach other, as depicted by arrow 724 c.

Similarly, for Band 2A, Zin2=R₄+jX₄ (with R₄≈1 and X₄≠0), andZin1=R′₄−jX₄ (with R′₄≈0 and X₄≠0), with +jX₄ and −jX₄ of Zin2 and Zin1being conjugates of each other, as depicted by arrow 724 d. For Band 2A,Zin2=R₅−jX₅ (with R₅≈1 and X₅≠0), and Zin1=R′5 jX₅ (with R′₅≈0 andX₅≠0), with −jX₅ and +jX₅ of Zin2 and Zin1 being conjugates of eachother, as depicted by arrow 724 e.

It is noted that in the foregoing examples of Zin1 and Zin2 for the fivebands of FIG. 6, if Zin1 for a given band is capacitive (i.e., impedanceis in a region below the horizontal line of the Smith chart), then Zin2for the same band is inductive (i.e., impedance is in a region above thehorizontal line of the Smith chart). Similarly, if Zin1 for a given bandis inductive, then Zin2 for the same band is capacitive.

In the example of FIGS. 4 and 6, suppose that each filter of a givengroup (e.g., the first group 721) is configured to provide the foregoingZin1 and Zin2 impedances for the first and second paths of the couplingcircuit 100. In some embodiments, the architecture 720 can be configuredsuch that some or all of capacitive and inductive impedances of Zin1 andZin2 are rotated toward desirable location(s) on a Smith chart. Forexample, a capacitive or inductive impedance close to a short circuitstate can be rotated towards such a short circuit state so as to providean impedance equal to, or approximately equal to, the short circuitimpedance. In another example, a capacitive or inductive impedance closeto a matched impedance state can be rotated towards such a matchedimpedance state so as to provide an impedance equal to, or approximatelyequal to, the matched impedance.

In some embodiments, the foregoing rotation of Zin1 and Zin2 impedancesfor the given group of filters can be implemented by, for example,configuring of another group (e.g., the second group 722), introductionof one or more phase shifting components, or some combination thereof.Examples of such phase shifting components are described herein ingreater detail.

FIGS. 7-15 show examples of architectures that can be implementedutilizing one or more features described in reference to the examples ofFIGS. 4-6.

For example, FIG. 7 shows an architecture 730 that can be implementedsimilar to the examples of FIGS. 4 and 6, where a first group of filters721 includes a plurality of filters, and a second group of filters 722includes a plurality of filters. FIG. 7 shows that in some embodiments,the architecture 730 can further include a first phase shifter 103implemented between the coupling circuit 100 and the first group offilters 721, and a second phase shifter 105 implemented between thecoupling circuit 100 and the second group of filters 722. Additionalexamples related to the architecture 730 of FIG. 7 are described hereinin greater detail.

In another example, FIG. 8 shows an architecture 732 that utilizes aplurality of coupling circuits 100 a, 100 b with a plurality of groupsof filters, where at least one group includes a plurality of filters forsupporting different bands. In the example of FIG. 8, a first couplingcircuit 100 a is shown to couple a common signal node 102 to first andsecond paths, with the first path including a group of one or morefilters 723, and the second path including a common signal node for asecond coupling circuit 100 b. The second coupling circuit 100 b isshown to couple its common signal node to its first and second paths,with the first path including a group of one or more filters 722, andthe second path including a group of one or more filters 721.

In the example of FIG. 8, phase shifters 103 a, 103 b are shown to beprovided along the first and second paths associated with the firstcoupling circuit 100 a. Similarly, phase shifters 103 c, 103 d are shownto be provided along the first and second paths associated with thesecond coupling circuit 100 b. It will be understood that in someembodiments, some or all of such paths associated with the couplingcircuits 100 a, 100 b can be implemented without phase shifter(s).Additional examples related to the architecture 732 of FIG. 8 aredescribed herein in greater detail.

In yet more examples, FIGS. 9-11 show architectures where a commonsignal node 102 of a coupling circuit 100 is coupled to an antenna, andfirst and second paths from the coupling circuit 100 are coupled to oneor more multiplexers 701. For the purpose of description, such one ormore multiplexers (701) can include one or more groups of filters, whereat least one of such group(s) includes a plurality of different bandfilters. It will be understood that while each path from a respectivecoupling circuit is shown to include a phase shifter, such a path may ormay not include a phase shifter.

In the example of FIG. 9, an architecture 734 can include a switchingcircuit 107 implemented along a path between the coupling circuit 100and the multiplexer(s) 701. FIGS. 12 and 13 show more specific examplesof such an architecture.

In the example of FIG. 10, an architecture 736 can include a switchingcircuit 109 implemented between the coupling circuit 100 and one or moreantennas. FIGS. 14 and 15 show more specific examples of such anarchitecture.

In the example of FIG. 11, an architecture 738 can include a switchingcircuit 107 implemented along a path between the coupling circuit 100and the multiplexer(s) 701, as well as a switching circuit 109implemented between the coupling circuit 100 and one or more antennas.Additional examples of such an architecture are described herein.

FIG. 12 shows an architecture 734 that can be a more specific example ofthe architecture 734 of FIG. 9. In the example of FIG. 12, a switch 107can be implemented between a coupling circuit 100 and a group of filters722, so as to allow selection of a filter among the filters within thesame group 722. For example, suppose that the group of filters 722includes Band 2A and Band 2B filters. The switch 107 can be configuredto allow the coupling circuit 100 to be coupled to either of such twofilters.

FIG. 13 shows an architecture 734 that can be another more specificexample of the architecture 734 of FIG. 9. In the example of FIG. 13, aswitch 107 can be implemented between a coupling circuit 100 and aplurality of groups of filters 722, so as to allow selection of a groupamong the groups. For example, suppose that the architecture 734includes three groups of filters 721, 722, 723. The switch 107 can beconfigured to, for example, allow the coupling circuit 100 to be coupledto the group 721 or the group 722. It will be understood that the group723 can also be switchably coupled to the coupling circuit 100 in asimilar manner.

In some embodiments, the architecture 734 of FIG. 13 can include one ormore switching function blocks to allow switchable selection of a filterwithin a given group. Similarly, in some embodiments, the architecture734 of FIG. 12 can include one or more switching function blocks toallow switchable selection of a group among a plurality of groups. Itwill be understood that in some embodiments, such filter-group selectionand filter-selection (within a given group) functionalities can beachieved by an appropriately configured switching network. Examplesrelated to such a switching network are described herein in greaterdetail.

FIG. 14 shows an architecture 736 that can be a more specific example ofthe architecture 736 of FIG. 10. In the example of FIG. 14, a switch 109can be implemented between a coupling circuit 100 and a plurality ofantennas (e.g., ANT1, ANT2), so as to allow selection of an antenna tobe coupled to a common signal node of the coupling circuit 100. In theexample of FIG. 14, first and second paths from the coupling circuit 100can be coupled to one or more multiplexers 701 as described herein.

FIG. 15 shows an architecture 736 that can be another more specificexample of the architecture 736 of FIG. 10. In the example of FIG. 15, aswitch 109 can be implemented between a common antenna (ANT) and aplurality of coupling circuits (e.g., 100 a, 100 b). Such aconfiguration can allow the common antenna (ANT) to be coupled to thecommon signal node of either of the coupling circuits 100 a, 100 b. Inthe example of FIG. 15, each of first and second paths from eachcoupling circuit (100 a or 100 b) can be coupled to a filter, amultiplexer, another coupling circuit, a switch, etc., including thevarious examples described herein.

FIGS. 16-18 show various examples of coupling circuits 100 that can beutilized in the various architectures as described herein. FIG. 16 showsthat in some embodiments, an architecture having one or more features asdescribed herein can include a coupling circuit 100 disclosed in PCTPublication No. WO2016/033427. More particularly, the coupling circuit100 can include two LC circuits that couple an input node 102 to ground.The first LC circuit can include a first inductance L1 (on the inputside) in series with a first capacitance C1 (on the ground side). Thesecond LC circuit can include a second capacitance C2 (on the inputside) in series with a second inductance L2 (on the ground side). A nodebetween L1 and C1 is shown to be coupled to a first path, and a nodebetween C2 and L2 is shown to be coupled to a second path.

FIG. 17A shows that in some embodiments, an architecture having one ormore features as described herein can include a coupling circuit 100having a resonator 111. In some embodiments, such a resonator canreplace a capacitance or an inductance in the coupling circuit 100 ofFIG. 16. For example, the coupling circuit 100 of FIG. 17A is shown toinclude a resonator 111 that replaces the capacitance C2 of the couplingcircuit 100 of FIG. 16. It will be understood that each of the otherelements L1, C1, L2 of the coupling circuit 100 of FIG. 17A may or maynot have the same value as the corresponding counterpart element (L1, C1or L2) of the coupling circuit 100 of FIG. 16.

FIG. 17B shows that in some embodiments, the resonator 111 of thecoupling circuit 100 of FIG. 17A can include an acoustic resonator suchas a bulk acoustic wave (BAW) resonator, any other BAW-based resonator,a surface acoustic wave (SAW) resonator (e.g., a temperature-compensatedSAW (TC-SAW) resonator, a leaky SAW (LSAW) resonator, a longitudinalLSAW (LLSAW) resonator, a trapped SAW resonator), any acoustic resonatorwith sub-2 μm piezoelectric layer on interface of supporting substrate,or some combination thereof. An example of an architecture having such aresonator in a coupling circuit is described herein in greater detail.

FIGS. 18A and 18B show that in some embodiments, an architecture havingone or more features as described herein can include a coupling circuit100 having a half bridge configuration. As disclosed in PCT PublicationNo. WO2016/033427, the coupling circuit 100 of FIG. 18A can beconfigured to provide a 3-pole low-pass filter functionality for thepath coupled to the node between L1 and C1. Examples related to anarchitecture having such a half-bridge coupling circuit are describedherein in greater detail.

Similarly, the coupling circuit 100 of FIG. 18B can be configured toprovide a 3-pole high-pass filter functionality for the path coupled tothe node between C2 and L2. Examples related to an architecture havingsuch a half-bridge coupling circuit are described herein in greaterdetail.

FIG. 19A shows an example architecture 740 that includes the half-bridgecoupling circuit 100 of FIG. 18A. In the example of FIG. 19A, thecoupling circuit 100 couples a common signal node 102 to a first groupof filters 701 through a node between L1 and C1. The common signal node102 is also shown to be directly coupled to a second group of filters702.

In the example of FIG. 19A, a phase shifter 103 is shown to be providedbetween the coupling circuit 100 and the first group of filters 701. Insome embodiments, such a phase shifter can be configured to accommodateor compensate for a phase shift associated with a filter within thefirst group 701.

FIG. 19B shows an example architecture 742 that includes the half-bridgecoupling circuit 100 of FIG. 18B. In the example of FIG. 19B, thecoupling circuit 100 couples a common signal node 102 to a second groupof filters 702 through a node between C2 and L2. The common signal node102 is also shown to be directly coupled to a first group of filters701.

In the example of FIG. 19A, a phase shifter 103 is shown to be providedbetween the coupling circuit 100 and the second group of filters 702. Insome embodiments, such a phase shifter can be configured to accommodateor compensate for a phase shift associated with a filter within thesecond group 702.

FIG. 20 shows an architecture 720 that is a more specific example of thearchitecture 720 of FIG. 4, utilizing the coupling circuit 100 of FIG.16. In the example of FIG. 20, a first group of filters 721 is shown toinclude three low frequency band duplexers, each having respectivetransmit (Tx) and receive (Rx) filters, for three bands F1, F2, F3.Thus, the first group of filters 721 includes three Rx filters forF1_Rx, F2_Rx, F3_Rx bands, and three Tx filters for F1_Tx, F2_Tx, F3_Txbands. Similarly, a second group of filters 722 is shown to include twohigh frequency band duplexers, each having respective transmit (Tx) andreceive (Rx) filters, for two bands F4, F5. Thus, the second group offilters 722 includes two Rx filters for F4_Rx, F5_Rx bands, and two Txfilters for F4_Tx, F5_Tx bands. For the purpose of description of theexample of FIG. 20, it will be assumed that the frequency bands F1, F2,F3, F4, F5 have successively higher frequency values (e.g.,middle-frequency value in a given band), such that F1<F2<F3<F4<F5.

In the example of FIG. 20, the coupling circuit 100 is shown to includea common signal node 102 that is between an inductance L1 and acapacitance C2. The common signal node 102 is shown to be coupled to anantenna 760. A first node between the inductance L1 and a capacitance C1is shown to be coupled to the first group of filters 721, so as to bepresented with a first impedance Zin1. A second node between thecapacitance C2 and an inductance L2 is shown to be coupled to the secondgroup of filters 722, so as to be presented with a second impedanceZin2. A node between the capacitance C1 and the inductance L2 is shownto be coupled to a ground.

Referring to the example of FIG. 20, suppose that a receive operationinvolves a signal being received through the antenna 760, and a selectedRx filter in each of the first and second groups 721, 722 is coupled tothe coupling circuit 100 for carrier aggregation. In such an examplecontext, each of such selected filters can be configured such thatimpedances Zin1 and Zin2 associated with the coupling circuit 100 are asdescribed herein in reference to FIGS. 4 and 6. Accordingly, FIG. 21shows scans of Zin1 and Zin2 impedances for the example architecture 720of FIG. 20, showing various complex part-conjugate nature of Zin1 andZin2 for each band.

FIGS. 22 and 23 show examples of how phase shifting functionality can beutilized in architectures that include a coupling circuit as describedherein. For example, FIG. 22 shows an architecture 730 that is similarto the architecture 720 of FIG. 20, but in which one or more phaseshifters can be utilized to better isolate a group of bands from one ormore other groups of bands.

In the example of FIG. 22, a first group of filters 721 is shown toinclude three low frequency band duplexers, and a second group offilters 722 is shown to include two high frequency band duplexers,similar to the example of FIG. 20. For such groups of filters (e.g., lowfrequency band filters for bands F1, F2, F3, and high frequency bandfilter for bands F4, F5), impedances Zin1 and Zin2 can be similar to theexample of FIGS. 20 and 21.

In the example of FIG. 22, a first phase shifter 103 can be implementedbetween the coupling circuit 100 and the first group of filters 721, anda second phase shifter 105 can be implemented between the couplingcircuit 100 and the second group of filters 722. Such first and secondphase shifters can be configured to provide improved isolation between athird group of filters (e.g., mid frequency bands) and each of the firstand second groups 721, 722. For example, the phase shifter 103 canprovide a shift in phase, such that an impedance Zin3 after the phaseshifter 103 is approximately an open circuit impedance for a midfrequency band signal, and a capacitive impedance for a high frequencyband signal. The phase shifter 105 can provide a shift in phase, suchthat an impedance Zin4 after the phase shifter 105 is approximately anopen circuit impedance for the mid frequency band signal, and aninductive impedance for a low frequency band signal. It is noted thatthe foregoing phase shifting configuration minimizes or reduces mutualloading between the mid frequency band and the high frequency band.

In another example, FIG. 23 shows an architecture 730 that is similar tothe architecture 730 of FIG. 22, but in which phase shiftingfunctionality can be implemented to be band-specific for at least someof the bands supported by first and second groups of filters 721, 722.In some embodiments, phase shifting elements 770 such as transmissionlines, L/C components and/or resonators can be configured forband-specific implementations. In some embodiments, such band-specificphase shifting functionality can result in improved performance of thecoupling circuit 100.

For example, for the first group of filters 721 in the architecture 730of FIG. 23, an inductance element and a transmission line can beconfigured and implemented for the Tx and Rx filters of the first band(F1), transmission lines can be configured and implemented for both ofthe Tx and Rx filters of the second band (F1), and a transmission lineand an inductance element can be configured and implemented for the Txand Rx filters of the third band (F3).

For the second group of filters 722 in the architecture 730 of FIG. 23,an inductance element and a transmission line can be configured andimplemented for the Tx and Rx filters of the first band (F4), and atransmission line and a resonator can be configured and implemented forthe Tx and Rx filters of the second band (F5).

FIG. 23 also shows that in some embodiments, a phase shifting element,such as a resonator, can be implemented as a part of a coupling circuit.For example, the coupling circuit 100 is shown to include a resonator111 implemented to replace a capacitance (e.g., C1 in FIG. 22). In someembodiments, the resonator 111 of the coupling circuit 100 and theresonator associated with the band-specific phase shifting elements 770can be configured to function operatively to provide improvedfunctionality of the coupling circuit.

In some embodiments, each of the foregoing resonators can be implementedas, for example, an acoustic resonator such as a bulk acoustic wave(BAVV) resonator or a surface acoustic wave (SAW) resonator (e.g., atemperature-compensated (TC) SAW resonator).

FIG. 24 shows an architecture 732 that can be a more specific example ofthe architecture 732 of FIG. 8, where a plurality of coupling circuitscan be utilized. In the example of FIG. 24, a first group of filters 721is shown to include one low frequency band duplexer, a second group offilters 722 is shown to include two mid frequency band duplexers, and athird group of filters 723 is shown to include two high frequency bandduplexers.

Referring to FIG. 24, the architecture 732 is shown to include a firstcoupling circuit 100 a having a common signal node 102 coupled to anantenna 760, a first path coupled to a common signal node (between L3and C4) of a second coupling circuit 100 b (from a node between L1 andC1), and a second path coupled to the third group of filters 723 (from anode between C2 and L2). The second coupling circuit 100 b is shown tohave its first path coupled to the first group of filters 721 (from anode between L3 and C3) and its second path coupled to the second groupof filters 722 (from a node between C4 and L4).

Configured in the foregoing manner, an impedance of Zin3 is presented inthe first path of the first coupling circuit 100 a, and an impedance ofZin4 is presented in the second path of the first coupling circuit 100a. Similarly, an impedance of Zin1 is presented in the first path of thesecond coupling circuit 100 b, and an impedance of Zin2 is presented inthe second path of the second coupling circuit 100 b.

In the example of FIG. 24, a group of filters associated with the firstpath of the first coupling circuit 100 a can be considered to includethe filters of the low frequency bands (721) and the filters of the midfrequency bands (722). Accordingly, the impedance Zin3 can have a valuethat is at or close to a load-matched impedance for low and midfrequency bands, and a value that is at or close to a short circuitstate for high frequency bands. The impedance Zin4 can have a value thatis at or close to a load-matched impedance for high frequency bands, anda value that is at or close to a short circuit state for low and midfrequency bands.

Also in the example of FIG. 24, the second coupling circuit 100 b isshown to support the low frequency band filters 721 and the midfrequency band filters 722 through its first and second paths.Accordingly, the impedance Zin1 can have a value that is at or close toa load-matched impedance for low frequency bands, and a value that is ator close to a short circuit state for mid frequency bands. The impedanceZin2 can have a value that is at or close to a load-matched impedancefor mid frequency bands, and a value that is at or close to a shortcircuit state for low frequency bands.

In the example of FIG. 24, a phase shifter is shown to be provided foreach path of each coupling circuit. More particularly, phase shifters103 b, 103 a are shown to be provided for the first and second paths ofthe first coupling circuit 100 a, and phase shifters 103 d, 103 c areshown to be provided for the first and second paths of the secondcoupling circuit 100 b. In some embodiments, such phase shifters can beselected to provide one or more desirable functionalities as describedherein. It will be understood that in some embodiments, an architecturesimilar to the example of FIG. 24 may include none of such phaseshifters, some of such phase shifters, or all of such phase shifters.

FIGS. 25-28 show examples of architectures having one or more switchingfunctionalities described herein in reference to FIGS. 9-15. Forexample, FIG. 25 show an architecture 734 that can be a more specificexample of the architectures 734 of FIGS. 9 and 12. In the example ofFIG. 25, a coupling circuit 100 is shown to couple a common signal node102 to a first group of filters 721 having three low frequency bandduplexers (F1, F2, F3) through a first path, and to a second group offilters 722 having two high frequency band duplexers (F4, F5) through asecond path. Such a second path is shown to include a switch 780configured to allow selection of a high frequency band (F4 or F5) amongthe bands of the second group 722.

In another example, FIG. 26 show an architecture 734 that can be a morespecific example of the architectures 734 of FIGS. 9 and 13. In theexample of FIG. 26, a coupling circuit 100 is shown to couple a commonsignal node 102 to a first group of filters 721 (having two lowfrequency band duplexers) or a second group of filters 722 (having twolow frequency band duplexers), through a first path, and to a thirdgroup of filters 723 (having a high frequency band duplexer) through asecond path. The first path is shown to include a switch 782 configuredto allow selection of the first group of filters 721 or the second groupof filters 722.

In yet another example, FIG. 27 shows an architecture 738 havingswitching functionalities described herein in reference to FIGS. 11, 13and 14. In the example of FIG. 27, a first group of low frequency bandfilters 721 a is shown to include two low frequency band duplexers, anda second group of low frequency band filters 721 b is shown to includetwo low frequency band duplexers. A first group of high frequency bandfilters 722 a is shown to include a high frequency band duplexer, and asecond group of high frequency band filters 722 b is shown to include ahigh frequency band duplexer. Accordingly, such groups of filters can begrouped into a first group having low frequency band duplexers (721 aand 721 b) coupled to a coupling circuit 100 through a first path, and asecond group having high frequency band duplexers (722 a and 722 b)coupled to the coupling circuit 100 through a second path.

In the example of FIG. 27, a switching network 786 is shown to beimplemented to provide switching functionalities between the couplingcircuit 100 and the foregoing first and second groups of filters. Moreparticularly, switches S1 and S2 of the switching network 786 can beoperated to provide coupling of the first group of low frequency bandfilters 721 a or the second group of low frequency band filters 721 b tothe coupling circuit 100 (through the first path). Similarly, switchesS3 and S4 of the switching network 786 can be operated to providecoupling of the first group of high frequency band filters 722 a or thesecond group of high frequency band filters 722 b to the couplingcircuit 100 (through the second path).

In the example of FIG. 27, a switching network 788 is shown to beimplemented to allow a common signal node 102 of the coupling circuit100 to be coupled to a first antenna 760 a or to a second antenna 760 b.For example, a switch S11 can be closed and a switch S12 can be openedto couple the common signal node 102 to the first antenna 760 a.Similarly, the switch S11 can be opened and the switch S12 can be closedto couple the common signal node 102 to the second antenna 760 b.

Referring to the example of FIG. 27, it will be understood that theforegoing switching networks 786 and 788 can be implemented in a numberof ways. In some embodiments, the switching networks 786 and 788 can bepart of a switching circuit indicated as 784, and such a switchingcircuit can be implemented on, for example, a die or a module.

FIG. 28 shows an example architecture 738 that includes switchingfunctionalities to allow a plurality of coupling circuits 100 a, 100 bto share a common antenna 760, and also to share a common group offilters 722. Suppose that an architecture design includes carrieraggregation capability between low frequency bands and high frequencybands. If such low frequency bands span sufficiently wide range infrequency, it may be desirable to split the low frequency bands into twosub-groups of low frequency bands, and pair each sub-group with a groupof the high frequency bands utilizing a respective coupling circuit.

Accordingly, in the example of FIG. 28, the common group of filters 722can include one or more high frequency bands. The first sub-group of lowfrequency filters can be 721 a, and the second sub-group of lowfrequency filters can be 721 b. Configured in the foregoing manner, thefirst sub-group of filters 721 a and the common group of filters 722 canbe coupled to a common signal node 102 a of the first coupling circuit100 a having appropriate values of L1, C1, C2, L2 selected toaccommodate such groups of filters. Similarly, the second sub-group offilters 721 b and the common group of filters 722 can be coupled to acommon signal node 102 b of the second coupling circuit 100 b havingappropriate values of L3, C3, C4, L4 selected to accommodate such groupsof filters. In some embodiments, phase shifters 103 a, 105 a, 103 b, 105b can be provides as shown and configured to provide desirable shifts inphases for improved performance.

Referring to the example of FIG. 28, a low-band/high-band carrieraggregation can involve the first sub-group 721 a or the secondsub-group 721 b. Accordingly, if the first sub-group 721 a is beingutilized, a switch 790 can allow the second path of the first couplingcircuit 100 a to be connected to the common group of filters 722, andthe second path of the second coupling circuit 100 b to be disconnectedfrom the common group of filters 722. Similarly, if the second sub-group721 b is being utilized, the switch 790 can allow the second path of thefirst coupling circuit 100 a to be disconnected from the common group offilters 722, and the second path of the second coupling circuit 100 b tobe connected to the common group of filters 722.

In the example of FIG. 28, the architecture 738 is shown to utilize acommon antenna 760. Accordingly, if the first coupling circuit 100 a isbeing utilized, its common signal node 102 a can be coupled to theantenna 760 by a switch 792, and a common signal node 102 b of thesecond coupling circuit 100 b can be uncoupled from the antenna 760 bythe switch 792. Similarly, if the second coupling circuit 100 b is beingutilized, its common signal node 102 b can be coupled to the antenna 760by the switch 792, and a common signal node 102 a of the first couplingcircuit 100 a can be uncoupled from the antenna 760 by the switch 792.

FIG. 29 shows an architecture 740 that can be a more specific example ofthe architecture 740 of FIG. 19A. In the example of FIG. 29, thearchitecture 740 is shown to include a first group of filters 721 havingthree mid frequency band duplexers and a second group of filters 722having two high frequency band duplexers. A half-bridge coupling circuit100 is shown to have its common signal node 102 coupled to an antenna760. A node between L1 and C1 of the coupling circuit 100 is shown to becoupled to the first group of filters 721 through a phase shifter 103.The second group of filters 722 is shown to be coupled to the commonsignal node 102.

Configured in the foregoing manner, impedance Zin1 is presented by thefirst path to the first group of filters 721, impedance Zin2 ispresented by the second path to the second group of filters 722, andimpedance Zin3 is presented to the common signal node 102 by theinductance L1. Accordingly, at a mid band frequency (for one of the midfrequency bands of the group 721), each of Zin1 and Zn3 has a value ator close to a matched load impedance, and Zin2 has an open circuitvalue. At a high band frequency (for one of the high frequency bands ofthe group 722), Zin2 has a value at or close to a matched loadimpedance, Zin1 has a short circuit value, and Zn3 has an open circuitvalue.

FIG. 30 shows an example architecture 800 that utilizes a number offeatures described herein. In the example of FIG. 30, two couplingcircuits 100 a, 100 b are shown to provide couplings between a commonantenna 760 and respective groups of filters. More particularly, thefirst coupling circuit 100 a is shown to provide coupling between theantenna 760 and groups of filters 721 a, 722; and the second couplingcircuit 100 b is shown to provide coupling between the antenna 760 andgroups of filters 721 b, 722.

Referring to FIG. 30, the group of filters 721 a is shown to include anumber of mid frequency band filters including duplexers for B3Tx/B3Rxand B1Tx/B1Rx bands, and a B32Rx band filter. The group of filters 721 bis shown to include a number of mid frequency band filters includingduplexers for B66Tx/B66Rx and B25Tx/B25Rx bands. The group of filters722 is shown to include a number of high frequency band filtersincluding a duplexers for B7Tx/B7Rx and B30Tx/B30Rx bands, and filtersB40TRx and B41TRx configured to support Tx and Rx operations inrespective bands. Accordingly, the foregoing grouping of filtersutilizes at least some of the features of the example of FIG. 28, wherea plurality of coupling circuits can be utilized to accommodatesplitting of a group of filters (low frequency band filters in FIG. 28,and mid frequency band filters in FIG. 30) into sub-groups of filters.

Accordingly, in the example of FIG. 30, the first coupling circuit 100 acan include inductances LMB, LHB and capacitances CMB, CHB as shown tosupport the foregoing mid frequency band and high frequency bandfilters. Similarly, the second coupling circuit 100 b can includeinductances LMB, LHB and capacitances CMB, CHB as shown to support theforegoing mid frequency band and high frequency band filters. It will beunderstood that each of LMB, LHB, CMB, CHB of the first coupling circuit100 a may or may not have the same value as respective one of LMB, LHB,CMB, CHB of the second coupling circuit 100 b.

In the example of FIG. 30, the architecture 800 is configured to allowat least some of the filters of the group 722 to be shared between thefirst and second coupling circuits 100 a, 100 b. More particularly, aswitch 802 can allow the B7Tx/B7Rx duplexer and the B41TRx filter to becoupled to the second path of the first coupling circuit 100 a, or tothe second path of the second coupling circuit 100 b.

In the example of FIG. 30, a switching circuit 804 (e.g., implemented asan antenna switching module (ASM)) can be configured to allow couplingof the antenna 760 to the first coupling circuit 100 a or to the secondcoupling circuit 100 b. More particularly, the common signal node 102 aof the first coupling circuit 100 a can be coupled to the antenna 760 byan appropriate operation of the switching circuit 804. Similarly, thecommon signal node 102 b of the second coupling circuit 100 b can becoupled to the antenna 760 by an appropriate operation of the switchingcircuit 804.

In the example of FIG. 30, the architecture 800 can include one or morecircuits that do not utilize a coupling circuit. For example, a group offilters 806 can include time-domain duplexing (TDD) filters such as midfrequency bands B34 and B39. Such a group of filters is shown to becoupled to the antenna 760 through the switching circuit 804 without acoupling circuit. In some embodiments, some or all of such TDD bands canbe individually, together with each other, with another FDD(frequency-domain duplexing) band (such as one or more filters of thegroup 722), or some combination thereof, utilizing the antenna 760.

In some embodiments, the architecture 800 of FIG. 30 can include phaseshifting elements such as transmission lines, L/C components and/orresonators configured to provide desirable functionalities, includingfunctionalities associated with either or both of the first and secondcoupling circuits 100 a, 100 b.

FIG. 31 shows that in some embodiments, one or more features asdescribed herein can be implemented in a radio-frequency (RF) module 300(e.g., a front-end module or an LNA module). The module 300 can includea packaging substrate 302 such as a laminate substrate. Such a modulecan include one or more LNAs 308. At least one of such LNAs can beconfigured to operate in a CA mode as described herein.

The module 300 can further include a carrier aggregation (CA) circuit100 having one or more features as described herein. Such a CA circuitcan be configured to provide CA functionality for the LNA 308 through adiplexer/filter assembly 306. Transmission lines 304 can be configuredto, for example, provide desired phase shifts in various signal paths,including those associated with inputs and output(s) of thediplexer/filter assembly 306. Although not shown, the module 300 canfurther include grounding switches for the CA circuit 100 to facilitateCA and non-CA operations as described herein.

In some implementations, an architecture, device and/or circuit havingone or more features described herein can be included in an RF devicesuch as a wireless device. Such an architecture, device and/or circuitcan be implemented directly in the wireless device, in one or moremodular forms as described herein, or in some combination thereof. Insome embodiments, such a wireless device can include, for example, acellular phone, a smart-phone, a hand-held wireless device with orwithout phone functionality, a wireless tablet, a wireless router, awireless access point, a wireless base station, etc. Although describedin the context of wireless devices, it will be understood that one ormore features of the present disclosure can also be implemented in otherRF systems such as base stations.

FIG. 32 depicts an example wireless device 500 having one or moreadvantageous features described herein. In some embodiments, suchadvantageous features can be implemented in a front-end (FE) or LNAmodule 300 as described herein. Such a module can include a CA circuit100 having one or more features as described herein. In someembodiments, such module can include more or less components than asindicated by the dashed box.

PAs in a PA module 512 can receive their respective RF signals from atransceiver 510 that can be configured and operated to generate RFsignals to be amplified and transmitted, and to process receivedsignals. The transceiver 510 is shown to interact with a basebandsub-system 508 that is configured to provide conversion between dataand/or voice signals suitable for a user and RF signals suitable for thetransceiver 510. The transceiver 510 is also shown to be connected to apower management component 506 that is configured to manage power forthe operation of the wireless device 500. Such power management can alsocontrol operations of the baseband sub-system 508 and other componentsof the wireless device 500.

The baseband sub-system 508 is shown to be connected to a user interface502 to facilitate various input and output of voice and/or data providedto and received from the user. The baseband sub-system 508 can also beconnected to a memory 504 that is configured to store data and/orinstructions to facilitate the operation of the wireless device, and/orto provide storage of information for the user.

In the example wireless device 500, the module 300 can include one ormore carrier aggregation-capable signal paths configured to provide oneor more functionalities as described herein. In some embodiments, atleast some of the signals received through a diversity antenna 530 canbe routed to one or more low-noise amplifiers (LNAs) 308 through suchcarrier aggregation-capable signal path(s). Amplified signals from theLNAs 308 are shown to be routed to the transceiver 510.

A number of other wireless device configurations can utilize one or morefeatures described herein. For example, a wireless device does not needto be a multi-band device. In another example, a wireless device caninclude additional antennas such as diversity antenna, and additionalconnectivity features such as Wi-Fi, Bluetooth, and GPS.

One or more features of the present disclosure can be implemented withvarious cellular frequency bands as described herein. Examples of suchbands are listed in Table 1. It will be understood that at least some ofthe bands can be divided into sub-bands. It will also be understood thatone or more features of the present disclosure can be implemented withfrequency ranges that do not have designations such as the examples ofTable 1.

TABLE 1 Tx Frequency Range Rx Frequency Range Band Mode (MHz) (MHz) B1FDD 1,920-1,980 2,110-2,170 B2 FDD 1,850-1,910 1,930-1,990 B3 FDD1,710-1,785 1,805-1,880 B4 FDD 1,710-1,755 2,110-2,155 B5 FDD 824-849869-894 B6 FDD 830-840 875-885 B7 FDD 2,500-2,570 2,620-2,690 B8 FDD880-915 925-960 B9 FDD 1,749.9-1,784.9 1,844.9-1,879.9 B10 FDD1,710-1,770 2,110-2,170 B11 FDD 1,427.9-1,447.9 1,475.9-1,495.9 B12 FDD699-716 729-746 B13 FDD 777-787 746-756 B14 FDD 788-798 758-768 B15 FDD1,900-1,920 2,600-2,620 B16 FDD 2,010-2,025 2,585-2,600 B17 FDD 704-716734-746 B18 FDD 815-830 860-875 B19 FDD 830-845 875-890 B20 FDD 832-862791-821 B21 FDD 1,447.9-1,462.9 1,495.9-1,510.9 B22 FDD 3,410-3,4903,510-3,590 B23 FDD 2,000-2,020 2,180-2,200 B24 FDD 1,626.5-1,660.51,525-1,559 B25 FDD 1,850-1,915 1,930-1,995 B26 FDD 814-849 859-894 B27FDD 807-824 852-869 B28 FDD 703-748 758-803 B29 FDD N/A 716-728 B30 FDD2,305-2,315 2,350-2,360 B31 FDD 452.5-457.5 462.5-467.5 B33 TDD1,900-1,920 1,900-1,920 B34 TDD 2,010-2,025 2,010-2,025 B35 TDD1,850-1,910 1,850-1,910 B36 TDD 1,930-1,990 1,930-1,990 B37 TDD1,910-1,930 1,910-1,930 B38 TDD 2,570-2,620 2,570-2,620 B39 TDD1,880-1,920 1,880-1,920 B40 TDD 2,300-2,400 2,300-2,400 B41 TDD2,496-2,690 2,496-2,690 B42 TDD 3,400-3,600 3,400-3,600 B43 TDD3,600-3,800 3,600-3,800 B44 TDD 703-803 703-803

It is noted that while various examples are described herein in thecontext of carrier aggregation of two or three bands, one or morefeatures of the present disclosure can also be implemented inconfigurations involving carrier aggregation of different numbers ofbands.

Unless the context clearly requires otherwise, throughout thedescription and the claims, the words “comprise,” “comprising,” and thelike are to be construed in an inclusive sense, as opposed to anexclusive or exhaustive sense; that is to say, in the sense of“including, but not limited to.” The word “coupled”, as generally usedherein, refers to two or more elements that may be either directlyconnected, or connected by way of one or more intermediate elements.Additionally, the words “herein,” “above,” “below,” and words of similarimport, when used in this application, shall refer to this applicationas a whole and not to any particular portions of this application. Wherethe context permits, words in the above Detailed Description using thesingular or plural number may also include the plural or singular numberrespectively. The word “or” in reference to a list of two or more items,that word covers all of the following interpretations of the word: anyof the items in the list, all of the items in the list, and anycombination of the items in the list.

The above detailed description of embodiments of the invention is notintended to be exhaustive or to limit the invention to the precise formdisclosed above. While specific embodiments of, and examples for, theinvention are described above for illustrative purposes, variousequivalent modifications are possible within the scope of the invention,as those skilled in the relevant art will recognize. For example, whileprocesses or blocks are presented in a given order, alternativeembodiments may perform routines having steps, or employ systems havingblocks, in a different order, and some processes or blocks may bedeleted, moved, added, subdivided, combined, and/or modified. Each ofthese processes or blocks may be implemented in a variety of differentways. Also, while processes or blocks are at times shown as beingperformed in series, these processes or blocks may instead be performedin parallel, or may be performed at different times.

The teachings of the invention provided herein can be applied to othersystems, not necessarily the system described above. The elements andacts of the various embodiments described above can be combined toprovide further embodiments.

While some embodiments of the inventions have been described, theseembodiments have been presented by way of example only, and are notintended to limit the scope of the disclosure. Indeed, the novel methodsand systems described herein may be embodied in a variety of otherforms; furthermore, various omissions, substitutions and changes in theform of the methods and systems described herein may be made withoutdeparting from the spirit of the disclosure. The accompanying claims andtheir equivalents are intended to cover such forms or modifications aswould fall within the scope and spirit of the disclosure.

1. A radio-frequency architecture comprising: a first group of pluralityof filters each configured to support a band such that a first frequencyrange covers the respective plurality of bands; a second group of one ormore filters each configured to support a band such that a secondfrequency range covers the respective one or more bands, each filter ofone of the first and second groups configured to provide an impedance ator near a short circuit impedance for a signal in each band of the othergroup, each filter of the other group configured to provide anapproximately open circuit impedance for a signal in each band of theone of the first and second groups; and a coupling circuit including acommon node and configured to couple the common node to one of the firstand second groups through a first path and to couple the common node tothe other group through a second path, the coupling circuit furtherconfigured such that the impedance provided by each filter of the one ofthe first and second groups for the signal in each band of the othergroup results in the signal being sufficiently excluded from the firstpath.
 2. The radio-frequency architecture of claim 1 wherein thecoupling circuit is further configured such that the approximately opencircuit impedance provided by each filter of the other group for thesignal in each band of the one of the first and second groups results inthe signal being substantially excluded from the second path.
 3. Theradio-frequency architecture of claim 1 wherein the first group is theone of the first and second groups and supports a frequency range thatis lower than a frequency range supported by the second group.
 4. Theradio-frequency architecture of claim 3 wherein the coupling circuitincludes an LC circuit that couples the common node to ground, the LCcircuit including an inductance L and a capacitance C in series suchthat the inductance L is between the common node and a first node andthe capacitance C is between the first node and the ground, the firstnode being coupled to the first group through the first path.
 5. Theradio-frequency architecture of claim 4 wherein the coupling circuit isconfigured such that the common node is coupled to the second groupthrough the second path.
 6. The radio-frequency architecture of claim 1wherein the second group is the one of the first and second groups andsupports a frequency range that is higher than a frequency rangesupported by the first group.
 7. The radio-frequency architecture ofclaim 6 wherein the coupling circuit includes an LC circuit that couplesthe common node to ground, the LC circuit including a capacitance C andan inductance L in series such that the capacitance C is between thecommon node and a second node and the inductance L is between the secondnode and the ground, the second node being coupled to the second groupthrough the second path.
 8. The radio-frequency architecture of claim 7wherein the coupling circuit is configured such that the common node iscoupled to the first group through the first path.
 9. Theradio-frequency architecture of claim 1 wherein each of either or bothof the first and second paths includes a phase shifter.
 10. Theradio-frequency architecture of claim 1 wherein the first path iscoupled to the first group such that a phase shifting element isprovided between the first path and each of the plurality of filters.11. The radio-frequency architecture of claim 10 wherein the second pathis coupled to the second group such that a phase shifting element isprovided between the second path and each of the one or more filters.12. The radio-frequency architecture of claim 10 wherein each phaseshifting element includes a transmission line, an LC component, or aresonator.
 13. The radio-frequency architecture of claim 12 wherein theresonator includes an acoustic resonator.
 14. The radio-frequencyarchitecture of claim 1 wherein the coupling circuit includes aresonator.
 15. The radio-frequency architecture of claim 1 furthercomprising a switching circuit implemented to provide a filter selectionfunctionality along either or both of the first and second paths. 16.The radio-frequency architecture of claim 15 wherein the switchingcircuit includes a switch configured to allow selection of a filteramong a plurality of filters within the same group such that theselected filter is coupled to the respective one of the first and secondpaths.
 17. The radio-frequency architecture of claim 15 wherein theswitching circuit includes a switch configured to allow coupling of aselected one of the first and second paths to the respective group or toa third group of one or more filters each configured to support a bandsuch that a third frequency range covers the respective one or morebands.
 18. The radio-frequency architecture of claim 15 wherein theswitching circuit includes a switch configured to allow selection of anantenna among a plurality of antennas such that the selected antennabecomes coupled to the common node of the coupling circuit.
 19. Apackaged module comprising: a packaging substrate configured to receivea plurality of components; and a radio-frequency circuit implemented onthe packaging substrate and including a first group of plurality offilters each configured to support a band such that a first frequencyrange covers the respective plurality of bands, and a second group ofone or more filters each configured to support a band such that a secondfrequency range covers the respective one or more bands, each filter ofone of the first and second groups configured to provide an impedance ator near a short circuit impedance for a signal in each band of the othergroup, each filter of the other group configured to provide anapproximately open circuit impedance for a signal in each band of theone of the first and second groups, the radio-frequency circuit furtherincluding a coupling circuit having a common node and configured tocouple the common node to the one of the first and second groups througha first path and to couple the common node to the other group through asecond path, the coupling circuit further configured such that theimpedance provided by each filter of the one of the first and secondgroups for the signal in each band of the other group results in thesignal being sufficiently excluded from the first path.
 20. (canceled)21. (canceled)
 22. A wireless device comprising: one or more antennas; afront-end module in communication with the one or more antennas andincluding a radio-frequency circuit having a first group of plurality offilters each configured to support a band such that a first frequencyrange covers the respective plurality of bands, and a second group ofone or more filters each configured to support a band such that a secondfrequency range covers the respective one or more bands, each filter ofone of the first and second groups configured to provide an impedance ator near a short circuit impedance for a signal in each band of the othergroup, each filter of the other group configured to provide anapproximately open circuit impedance for a signal in each band of theone of the first and second groups, the radio-frequency circuit furtherincluding a coupling circuit having a common node and configured tocouple the common node to the one of the first and second groups througha first path and to couple the common node to the other group through asecond path, the coupling circuit further configured such that theimpedance provided by each filter of the one of the first and secondgroups for the signal in each band of the other group results in thesignal being sufficiently excluded from the first path; and a receiverconfigured to process one or more signals associated with the first andsecond group.
 23. (canceled)